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MICRF211
3V, QwikRadio(R) 433.92 MHz Receiver
General Description
The MICRF211 is a general purpose, 3V QwikRadio Receiver that operates at 433.92MHz with typical sensitivity of -110dBm. The MICRF211 functions as a super-heterodyne receiver for OOK and ASK modulation up to 10kbps. The down-conversion mixer also provides image rejection. All post-detection data filtering is provided on the MICRF211. Any one-of-four filter bandwidths may be selected externally by the user in binary steps, from 1.25kHz to 10kHz. The user need only configure the device with a set of easily determined values, based upon data rate, code modulation format, and desired duty-cycle operation.
Features
* * * * * * * * -110 dBm sensitivity, 1kbps and BER 10E-02 Image Rejection Mixer Frequency from 380MHz to 450MHz Low power, 6.0mA @ 433.92MHz, continuous on data rates to 10kbps (Manchester Encoded) Analog RSSI Output No IF filter required Excellent selectivity and noise rejection Low external part count
Ordering Information
Part Number MICRF211AYQS Temperature Range -40 to +105C Package 16-Pin QSOP
_______________________________________________________________________________________________
Typical Application
433.92 MHz, 1kHz Baud Rate Example
QwikRadio is a registered trademark of Micrel, Inc. Certain of the QwikRadio ICs were developed under a development agreement with AIT of Orlando, FL. Micrel Inc. * 2180 Fortune Drive * San Jose, CA 95131 * USA * tel +1 (408) 944-0800 * fax + 1 (408) 474-1000 * http://www.micrel.com
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MICRF211
Pin Configuration
MICRF211AYQS
Pin Description
16-Pin QSOP 1 2 3 4 5 6 7 8 9 10 11 12 Pin Name RO1 GNDRF ANT GNDRF VDD SQ SEL0 SHDN GND DO SEL1 CTH Pin Function Reference resonator input connection to Colpitts oscillator stage. May also be driven by external reference signal of 1.5V p-p amplitude maximum. Negative supply connection associated with ANT RF input. RF signal input from antenna. Internally AC coupled. It is recommended that a matching network with an inductor -to-RF ground is used to improve ESD protection. Negative supply connection associated with ANT RF input. Positive supply connection for all chip functions. Squelch control logic input with an active internal pull-up when not shut down. Logic control input with active internal pull-up. Used in conjunction with SEL1 to control the demodulator low pass filter bandwidth. (See filter table for SEL0 and SEL1 in application section) Shutdown logic control input. Active internal pull-up. Negative supply connection for all chip functions except RF input. Demodulated data output. Logic control input with active internal pull-up. Used in conjunction with SEL0 to control the demodulator low pass filter bandwidth. (See filter table for SEL0 and SEL1 in application section) Demodulation threshold voltage integration capacitor connection. Tie an external capacitor across CTH pin and GND to set the settling time for the demodulation data slicing level. Values above 1nF are recommended and should be optimized for data rate and data profile. AGC filter capacitor connection. CAGC capacitor, normally greater than 0.47F, is connected from this pin to GND Received signal strength indication output. Output is from a buffer with 200 typical output impedance. Not Connected (Connect to Ground) Reference resonator input connection to Colpitts oscillator stage, 7pF, in parallel with low resistance MOS switch-to-GND, during normal operation. Driven by startup excitation circuit during the internal startup control sequence.
13 14 15 16
CAGC RSSI NC RO2
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MICRF211
Absolute Maximum Ratings(1)
Supply Voltage (VDD) .................................................+5V Input Voltage .............................................................+5V Junction Temperature ......................................... +150C Lead Temperature (soldering, 10sec.) .................. 260C Storage Temperature (TS) .....................-65C to +150C Maximum Receiver Input Power ........................+10dBm ESD Rating(3) .................................................. 2KV CDM ...................................................200V HBM ................................ 100V Machine Model
Operating Ratings(2)
Supply voltage (VDD) ..............................+3.0V to +3.6V Ambient Temperature (TA) ................. -40C to +105C Input Voltage (VIN)........................................ 3.6V (Max) Maximum Input RF Power................................ -20dBm
Electrical Characteristics(4)
Specifications apply for 3.0V < VDD < 3.6V, VSS = 0V, CAGC = 4.7F, CTH = 0.1F, fRX = 433.92 MHz, unless otherwise noted. Bold values indicate -40C - TA - 105C. 1kbps data rate (Manchester encoded), reference oscillator frequency = 13.52127MHz. Symbol ISS ISHUT Parameter Operating Supply Current Shut down Current Image Rejection 1st IF Center Frequency Receiver Sensitivity @ 1kbps IF Bandwidth Antenna Input Impedance Receive Modulation Duty Cycle AGC Attack / Decay Ratio AGC pin leakage current AGC Dynamic Range Reference Oscillator Reference Oscillator Frequency Reference Oscillator Input Impedance Reference Oscillator Input Range Reference Oscillator Source Current fRX = 433.92 MHz Crystal Load Cap = 10pF
13.52127
Condition Continuous Operation, fRX = 433.92MHz
Min
Typ 6.0 0.5 20
Max
Units mA A dB MHz dBm kHz
RF/IF Section
fRX = 433.92MHz fRX = 433.92MHz (matched to 50 ) BER=10-2 fRX = 433.92MHz fRX = 433.92MHz Note 5 tATTACK / tDECAY TA = 25C TA = +105C RFIN @ -40dBm RFIN @ -100dBm 20
1.2 -110 330 19 - j174 80 0.1 2 800 1.15 1.70
%
nA nA V V
MHz k 1.5 Vp-p A
300 0.2 V(REFOSC) = 0V 3.5
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Demodulator Symbol Parameter CTH Source Impedance CTH Leakage Current Demodulator Filter Bandwidth @ 434MHz Digital / Control Functions DO pin output current Output rise and fall times RSSI RSSI DC Output Voltage Range RSSI response slope RSSI Output Current RSSI Output Impedance RSSI Response Time
Note 1. Note 2. Note 3. Note 4. Note 5.
Condition FREFOSC = 13.52127MHz TA = 25C TA = +105C Programmable, see application section
Min
Typ 120 2 800
Max
Units k nA nA Hz
1625
13000
source @ 0.8 Vdd sink @ 0.2 Vdd CI = 15pF, pin DO, 10-90%
As output
260 600 2
A sec
0.4 to 2 -110dBm to -40dBm 25 400 200 50% data duty cycle, input power to Antenna = -20dBm 0.3
V
mV/dB
A sec
Exceeding the absolute maximum rating may damage the device. The device is not guaranteed to function outside of its operating rating. Device is ESD sensitive. Use appropriate ESD precautions. Exceeding the absolute maximum rating may damage the device. Sensitivity is defined as the average signal level measured at the input necessary to achieve 10-2 BER (bit error rate). The input signal is defined as a return-to-zero (RZ) waveform with 50% average duty cycle (Manchester encoded) at a data rate of 1kbps. When data burst does not contain preamble, duty cycle is defined as total duty cycle, including any "quiet" time between data bursts. When data bursts contain preamble sufficient to charge the slice level on capacitor CTH, then duty cycle is the effective duty cycle of the burst alone. [For example, 100msec burst with 50% duty cycle, and 100msec "quiet" time between bursts. If burst includes preamble, duty cycle is TON/(TON+tOFF)= 50%; without preamble, duty cycle is TON/(TON+ TOFF + TQUIET) = 50msec/(200msec)=25%. TON is the (Average number of 1's/burst) x bit time, and TOFF = TBURST - TON.)
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Typical Characteristics
Sensitivity Graphs
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Functional Diagram
Figure 1. Simplified Block Diagram.
Functional Description
Figure 1. Simplified Block Diagram that illustrates the basic structure of the MICRF211. It is made of three sub-blocks; Image Rejection UHF Down-converter, the OOK Demodulator, and Reference and Control Logics. Outside the device, the MICRF211 requires only three components to operate: two capacitors (CTH, and CAGC) and the reference frequency device, usually a quartz crystal. An additional five components may be used to improve performance. These are: power supply decoupling capacitor, two components for the matching network, and two components for the pre-selector band pass filter.
is set to 32 times the crystal reference frequency via a phase-locked loop synthesizer with a fully integrated loop filter. Image Reject Filter and Band-Pass Filter The IF ports of the mixer produce quadrature down converted IF signals. These IF signals are low-pass filtered to remove higher frequency products prior to the image reject filter where they are combined to reject the image frequencies. The IF signal then passes through a third order band pass filter. The IF center frequency is 1.2MHz. The IF BW is 330kHz @ 433.92MHz, and this varies with RF operating frequency. The IF BW can be calculated via direct scaling:
Receiver Operation
LNA The RF input signal is AC-coupled into the gate circuit of the grounded source LNA input stage. The LNA is a Cascoded NMOS. Mixers and Synthesizer The LO ports of the Mixers are driven by quadrature local oscillator outputs from the synthesizer block. The local oscillator signal from the synthesizer is placed on the low side of the desired RF signal to allow suppression of the image frequency at twice the IF frequency below the wanted signal. The local oscillator March 2007 6
BWIF = BWIF@433.92 MHz x
Operating Freq (MHz) 433.92
These filters are fully integrated inside the MICRF211. After filtering, four active gain controlled amplifier stages enhance the IF signal to proper level for demodulation. OOK Demodulator The demodulator section is comprised of detector, programmable low pass filter, slicer, and AGC comparator. Detector and Programmable Low-Pass Filter The demodulation starts with the detector removing the
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Micrel carrier from the IF signal. Post detection, the signal becomes base band information. The programmable low-pass filter further enhances the base band information. There are four programmable low-pass filter BW settings: 1625Hz, 3250Hz, 6500Hz, 13000Hz for 433.92MHz operation. Low pass filter BW will vary with RF Operating Frequency. Filter BW values can be easily calculated by direct scaling. See equation below for filter BW calculation:
Operating Freq (MHz) BWOperating Freq = BW@433.92MHz* 433.92
MICRF211 When the output signal is less than 750mV thresh-hold, 1.5A current is sourced into the external CAGC capacitor. When the output signal is greater than 750mV, a 15A current sink discharges the CAGC capacitor. The voltage developed on the CAGC capacitor acts to adjust the gain of the mixer and the IF amplifier to compensate for RF input signal level variation. Reference Control There are 2 components in Reference and Control subblock: 1) Reference Oscillator and 2) Control Logic through parallel Inputs: SEL0, SEL1, SHDN Reference Oscillator
It is very important to choose the filter setting that best fits the intended data rate to minimize data distortion. Demod BW is set at 13000Hz @ 433.92MHz as default (assuming both SEL0 and SEL1 pins are floating). The low pass filter can be hardware set by external pins SEL0 and SEL1.
SEL0 0 1 0 1 SEL1 0 0 1 1 Demod BW (@ 434MHz) 1625Hz 3250Hz 6500Hz 13000Hz - default
Table 1: Demodulation BW Selection
Slicer, Slicing Level and Squelch The signal prior to slicer is still linear demodulated AM. Data slicer converts this signal into digital "1"s and "0"s by comparing with the threshold voltage built up on the CTH capacitor. This threshold is determined by detecting the positive and negative peaks of the data signal and storing the mean value. Slicing threshold default is 50%. After the slicer the signal is now digital OOK data. During long periods of "0"s or no data period, threshold voltage on the CTH capacitor may be very low. Large random noise spikes during this time may cause erroneous "1"s at DO pin. Squelch pin when pull down low will suppress these errors. AGC Comparator The AGC comparator monitors the signal amplitude from the output of the programmable low-pass filter.
Figure 2: Reference Oscillator Circuit
The reference oscillator in the MICRF211 (Figure 2) uses a basic Colpitts crystal oscillator configuration with MOS transconductor to provide negative resistance. All capacitors shown in Figure 2 are integrated inside MICRF211. R01 and R02 are external pins of MICRF211. User only needs to connect reference oscillation crystal. Reference oscillator crystal frequency can be calculated: FREF OSC = FRF/(32 + 1.1/12) For 433.92 MHz, FREF OSC = 13.52127 MHz. To operate the MICRF211 with minimum offset, crystal frequencies should be specified with 10pF loading capacitance.
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Application Information
Figure 3 - QR211HE1 Application Example, 433.92 MHz
The MICRF211 can be fully tested by using one of many evaluation boards designed at Micrel for this device. As an entry level, the QR211HE1 (Figure 3) offers a good start for most applications. It has a helical PCB antenna with its matching network, a band-pass-filter front-end as a pre-selector filter, matching network and the minimum components required to make the device work, which are a crystal, Cagc, and Cth capacitors. By removing the matching network of the helical PCB antenna (C9 and L3), a whip antenna (ANT2) or a RF connector (J2) can be used instead. Figure 3 shows the entire schematic of it for 433.92MHz. Other frequencies can be used and the values needed are in the tables below. Capacitor C9 and inductor L3 are the passive elements for the helical PCB matching network. A tight tolerance is recommended for these devices, like 2% for the inductor and 0.1pF for the capacitor. PCB variations may require different values and optimization. Table 2 shows the matching elements for the device frequency range. For additional information look for Small PCB Antennas for Micrel RF Products application note.
Freq (MHz) 390.0 418.0 433.92 C9 (pF) 1.2 1.2 1.5 L3(nH) 43 36 30
which reduces the receiver performance. It is calculated by the parallel resonance equation f = 1/(2xPIx(SQRT L1xC8)). Table 3 shows the most used frequency values.
Freq (MHz) 390.0 418.0 433.92 C8 (pF) 6.8 6.0 5.6 L1(nH) 24 24 24
Table 3. Band-Pass-Filter Front-End Values
Table 2. Matching Values for the Helical PCB Antenna
To use another antenna, like the whip kind, remove C9 and place the whip antenna in the hole provided in the PCB. Also, a RF signal can be injected there. L1 and C8 form the pass-band-filter front-end. Its purpose is to attenuate undesired outside band noise March 2007 8
There is no need for the band-pass-filter front-end for applications where it is proven that the outside band noise does not cause a problem. The MICRF211 has image reject mixers which improve significantly the selectivity and rejection of outside band noise. Capacitor C3 and inductor L2 form the L-shape matching network. The capacitor provides additional attenuation for low frequency outside band noise and the inductor provides additional ESD protection for the antenna pin. Two methods can be used to find these values, which are matched close to 50. One method is done by calculating the values using the equations below and another by using a Smith chart. The latter is made easier by using software that plots the values of the components C8 and L1, like WinSmith by Noble Publishing. To calculate the matching values, one needs to know the input impedance of the device. Table 4 shows the input impedance of the MICRF211 and suggested matching values for the most used frequencies. These suggested values may be different if the layout is not exactly the same as the one made here.
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Freq (MHz) 390.0 418.0 433.92 C3 (pF) 1.5 1.5 1.5 L2(nH) 47 43 39 Z device () 22.5 - j198.5 21.4 - j186.1 18.6 - j174.2
MICRF211
Figure 4: device's input impedance, Z = 18.6 - j174.2
Table 4: matching values for the most used frequencies
Second, we plot the shunt inductor (39nH) and the series capacitor (1.5pF) for the desired input impedance (Figure 5). We can see the matching leading to the center of the Smith Chart or close to 50.
For the frequency of 433.92MHz, the input impedance is Z = 18.6 - j174.2, then the matching components are calculated by, Equivalent parallel = B = 1/Z = 0.606 + j5.68 msiemens Rp = 1 / Re (B); Xp = 1 / Im (B) Rp = 1.65k; Xp = 176.2 Q = SQRT (Rp/50 + 1) Q = 5.831 Xm = Rp / Q Xm = 282.98 Resonance Method For L-shape Matching Network Lc = Xp / (2xPixf); Lp = Xm / (2xPixf) L2 = (LcxLp) / (Lc + Lp); C3 = 1 / (2xPixfxXm) L2 = 39.8nH C3 = 1.3pF Doing the same calculation example with the Smith Chart, it would appear as follows, First, we plot the input impedance of the device, (Z = 18.6 - j174.2) @ 433.92MHz.(Figure 4).
Figure 5. Plotting the Shunt Inductor and Series Capacitor.
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MICRF211 injection (32 x 13.52127MHz = 432.68MHz), that is, its frequency is below the RF carrier frequency and the image frequency is below the LO frequency. See Figure 6. The product of the incoming RF signal and local oscillator signal will yield the IF frequency, which will be demodulated by the detector of the device.
Crystal Y1 or Y1A (SMT or leaded respectively) is the reference clock for all the device internal circuits. Crystal characteristics of 10pF load capacitance, 30ppm, ESR < 50, -40C to +105C temperature range are desired. Table 5 shows the crystal frequencies and one of Micrel's approved crystal manufacturers (www.hib.com.br). The oscillator of the MICRF211 is a Colpitts type. It is very sensitive to stray capacitance loads. Thus, very good care must be taken when laying out the printed circuit board. Avoid long traces and ground plane on the top layer close to the REFOSC pins RO1 and RO2. When care is not taken in the layout, and crystals from other vendors are used, the oscillator may take longer times to start as well as the time to good data in the DO pin to show up. In some cases, if the stray capacitance is too high (> 20pF), the oscillator may not start at all. The crystal frequency is calculated by REFOSC = RF Carrier/(32+(1.1/12)). The local oscillator is low side
REFOSC (MHz) 12.15269 13.02519 13.52127 Carrier (MHz) 390.0 418.0
Figure 6. Low Side Injection Local Oscillator.
HIB Part Number SA-12.152690-F-10-H-30-30-X SA-13.025190-F-10-H-30-30-X
433.92 SA-13.521270-F-10-H-30-30-X Table 5. Crystal Frequency and Vendor Part Number.
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Micrel JP1 and JP2 are the bandwidth selection for the demodulator bandwidth. To set it correctly, it is necessary to know the shortest pulse width of the encoded data sent in the transmitter. Like in the example of the data profile in the figure 7 below, PW2 is shorter than PW1, so PW2 should be used for the demodulator bandwidth calculation which is found by 0.65/shortest pulse width. After this value is found, the setting should be done according to Table 6. For example, if the pulse period is 100sec, 50% duty cycle, the pulse width will be 50sec (PW = (100sec x 50%) / 100). So, a bandwidth of 13kHz would be necessary (0.65 / 50sec). However, if this data stream had a pulse period with 20% duty cycle, the bandwidth required would be 32.5kHz (0.65 / 20sec), which exceeds the maximum bandwidth of the demodulator circuit. If one tries to exceed the maximum bandwidth, the pulse would appear stretched or wider.
SEL0 JP1 SEL1 JP2 Demod. BW (hertz) 1625 3250 6500 13000 Shortest Pulse (sec) 400 200 100 50 Maximum baud rate for 50% Duty Cycle (hertz) 1250 2500 5000 10000 SEL0 JP1 SEL1 JP2 Demod. BW (hertz) 1460 2921 5842 11684 Shortest Pulse (sec) 445 223 111 56
MICRF211
Maximum baud rate for 50% Duty Cycle (Hertz) 1123 2246 4493 8987
Short Open Short Open
Short Short Open Open
Table 8. JP1 and JP2 setting, 390.0 MHz.
Capacitors C6 and C4, CTH and CAGC respectively provide time base reference for the data pattern received. These capacitors are selected according to data profile, pulse duty cycle, dead time between two received data packets, and if the data pattern has or does not have a preamble. See Figure 7, example of a data profile.
Short Open Short Open
Short Short Open Open
Figure 7. Example of a Data Profile.
Table 6. JP1 and JP2 setting, 433.92 MHz.
Other frequencies will have different demodulator bandwidth limits, which are derived from the reference oscillator frequency. Table 7 and Table 8 below shows the limits for the other two most used frequencies.
SEL0 JP1 SEL1 JP2 Demod. BW (hertz) 1565 3130 6261 12523 Shortest Pulse (sec) 416 208 104 52 Maximum baud rate for 50% Duty Cycle (hertz) 1204 2408 4816 9633
For best results the capacitors should always be optimized for the data pattern used. As the baud rate increases, the capacitor values decrease. Table 9 shows suggested values for Manchester Encoded data, 50% duty cycle.
SEL0 JP1 Short Open Short Open SEL1 JP2 Short Short Open Open Demod. BW (hertz) 1625 3250 6500 13000 Cth Cagc
Short Open Short Open
Short Short Open Open
100nF 47nF 22nF 10nF
4.7F 2.2F 1F 0.47F
Table 7. JP1 and JP2 setting, 418.0 MHz.
Table 9. Suggested CTH and CAGC Values.
JP3 is a jumper used to configure the digital squelch function. When it is high, there is no squelch applied to the digital circuits and the DO (data out) pin has a hash signal. When the pin is low, the DO pin activity is March 2007 11
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Micrel considerably reduced. It will have more or less than shown in the figure below depending on the outside band noise. The penalty for using squelch is a delay in getting a good signal in the DO pin, that is, it takes longer for the data to show up. The delay is dependent upon many factors such as RF signal intensity, data profile, data rate, CTH and CAGC capacitor values, and outside band noise. See Figure 8 and Figure 9 below.
MICRF211 which form a voltage divider for the AGC pin. One can force a voltage in this AGC pin to purposely decrease the device sensitivity. Special care is needed when doing this operation, as an external control of the AGC voltage may vary from lot to lot and may not work the same for several devices. Three other pins are worthy of comment. They are the DO, RSSI, and shut down pins. The DO pin has a driving capability of 0.4mA. This is good enough for most of the logic family ICs in the market today. The RSSI pin provides a transfer function of the RF signal intensity vs voltage. It is very useful to determine the signal to noise ratio of the RF link, crude range estimate from the transmitter source and AM demodulation, which requires a low CAGC capacitor value. The shut down pin (SHDN) is useful to save energy. When its level close to VDD (SHDN = 1), the device is not in operation. Its DC current consumption is less than 1A (do not forget to remove R3). When toggling from high to low, there will be a time required for the device to come to steady state mode, and a time for data to show up in the DO pin. This time will be dependent upon many things such as temperature, crystal used, and if the there is an external oscillator with faster startup time. Normally, with the crystal vendors suggested, the data will show up in the DO pin around 1msec time, and 2msec over the temperature range of the device. When using an external oscillator or reference oscillator signal, the time is reduced considerably and can be around 140sec. See Figures Figure 10 and 11.
Figure 8. Data Out Pin with No Squelch (SQ = 1).
Figure 9. Data Out Pin with Squelch (SQ = 0).
Other components used are C5, which is a decoupling capacitor for the Vdd line, R4 reserved for future use and not needed for the evaluation board, R3 for the shutdown pin (SHDN = 0, device is operation), which can be removed if that pin is connected to a microcontroller or an external switch, R1 and R2
Figure 10: Time-to-Good Data After Shut Down Cycle, Room Temperature.
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Figure 11. Time to Good Data, External Oscillator, Room Temperature.
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Micrel PCB Considerations and Layout Figure 12 to 17 below show some of the printed circuit layers for the QR211HE1 board. Use the Gerber files provided (downloadable from Micrel Website) which have the remaining layers needed to fabricate this board. When copying or making your own boards, make traces as short as possible. Long traces alter the matching network and the values suggested are no longer valid. Suggested Matching Values may vary due to PCB variations. A PCB trace 100 mills (2.5mm) long has about 1.1nH inductance. Optimization should always be done with exhaustive range tests. Make individual ground connections to the ground plane with a Via for each ground connection. Do not share Vias with ground connections. Each ground
MICRF211
connection = 1 via or more vias. Ground plane must be solid and possibly without interruptions. Avoid ground plane on top next to the matching elements. It normally adds additional stray capacitance which changes the matching. Do not use phenolic material, only FR4 or better materials. Phenolic material is conductive above 200MHz. RF path should be as straight as possible avoiding loops and unnecessary turns. Separate ground and VDD lines from other circuits (microcontroller, etc). Known sources of noise should be laid out as far as possible from the RF circuits. Avoid thick traces, the higher the frequency, the thinner the trace should be in order to minimize losses in the RF path.
Figure 12. QR211HE1 Top Layer.
Figure 13. QR211HE1 Bottom Layer, Mirror Image.
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MICRF211
Figure 14. QR211HE1 Top Silkscreen Layer.
Figure 15. QR211HE1 Bottom Silkscreen Layer, Mirror Image.
Figure 16: QR211HE1 Dimensions.
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QR211HE1 Bill of Materials, 433.92 MHz
Item ANT1 ANT2 C3,C9 C4 C6,C5 C8 JP1,JP 2 JP3 J2 J3 L1 L2 L3 R1,R2, R4 R3 Y1 Y1A U1 HCM49 HC49 MICRF211AYQS Vishay www.hib.com.br www.hib.com.br Micrel Semiconductor Coilcraft / Murata / ACT1 Coilcraft / Murata / ACT1 Coilcraft / Murata / ACT1 MuRata Murata / Vishay Murata / Vishay Murata Vishay Part Number Manufacturer Description Helical PCB Antenna Pattern (np)50-ohm Ant 0.1F, 0402/0603 0.1F, 0402/0603 5.6pF, 0402/0603 short, 0402, 0 resistor open, 0402, not placed (np) not placed CON6 24nH 5%, 0402/0603 39nH 5%, 0402/0603 30nH 2%, 0402/0603 (np) 0402, not placed 100k , 0402 168mm 20 AWG, rigid wire 1.5pF , 0402/0603 Qty. 1 1 2 1 2 1 2 1 1 1 1 1 1 3 1 1 1 1
(np)13.52127MHz Crystal 13.52127MHz Crystal QSOP16
Table 10. QR211HE1 Bill of Materials, 433.92 MHz.
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Package Information
QSOP16 Package Type (AQS16)
MICREL, INC. 2180 FORTUNE DRIVE SAN JOSE, CA 95131 USA
TEL +1 (408) 944-0800 FAX +1 (408) 474-1000 WEB http:/www.micrel.com
The information furnished by Micrel in this data sheet is believed to be accurate and reliable. However, no responsibility is assumed by Micrel for its use. Micrel reserves the right to change circuitry and specifications at any time without notification to the customer. Micrel Products are not designed or authorized for use as components in life support appliances, devices or systems where malfunction of a product can reasonably be expected to result in personal injury. Life support devices or systems are devices or systems that (a) are intended for surgical implant into the body or (b) support or sustain life, and whose failure to perform can be reasonably expected to result in a significant injury to the user. A Purchaser's use or sale of Micrel Products for use in life support appliances, devices or systems is at Purchaser's own risk and Purchaser agrees to fully indemnify Micrel for any damages resulting from such use or sale. (c) 2007 Micrel, Incorporated.
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Revision History
Date
Edits by:
Revision Number
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